AN UNSTRUCTURED APPROACH

AN UNSTRUCTURED APPROACH

Let the closed loop of Figure 11.5, where K(s) and G(s) are the con­troller and the plant. A block of neglected dynamics A(s)is added at the plant inputs. This closed loop is first equivalently transformed into the standard interconnection structure M(s) – Д(в) of Figure П. б.а. M(s) is the transfer matrix seen by the model perturbation A(s) in Figure 11.5. A necessary and sufficient condition of stability is provided by the small gain theorem at frequency u:

AN UNSTRUCTURED APPROACH

It was assumed above that A(s) is an unstructured model perturbation. Nevertheless, a specific structure can be given a posteriori to Д(з):

I + Д(з) = diag(e ^’)

AN UNSTRUCTURED APPROACH Подпись: (11.22)

or:

AN UNSTRUCTURED APPROACH

The idea is thus to introduce phases фі in order to compute a MIMO phase margin with equation (11.20). When combining equations (11.20) and (11.22), one obtains:

AN UNSTRUCTURED APPROACH

Let:

A MIMO phase margin at frequency w is:

Подпись: (11.25) (11.26) (11.27) фі < 2 Arcsin(a{<jj)/2) Vi If the following structure is now given to Д(з):

I + Д(з) = diag{e~ns)

and using фі = шті, a MIMO delay margin at frequency ш is:

Подпись: i! <Подпись: ViArcsin(a(u>) / 2)

Remarks:

(i) ifa(cu) > 2, the MIMO phase margin is ± 180 degrees, and the MIMO delay margin is infinite.

(ii)

Подпись: i.e.: Подпись: (I + A(s)) 1 = diag(e ■?T<S) Д(в) = diag(e^TiS — 1) Подпись: (11.28)

MIMO phase or delay margins can also be computed with an inverse model perturbation at the plant inputs (see Figure 11.7). In this case, the delays are to be introduced as:

Direct model perturbations rather account for high frequency model un­certainties, whereas inverse model perturbations rather represent low fre­quency model uncertainties (Doyle et al., 1982). As a consequence, bet­ter estimates of the delay margin can be expected with an inverse (resp. direct) model perturbation at low (resp. high) frequencies (see section

3.

AN UNSTRUCTURED APPROACH

).

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